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50 mhz to 2 ghz quadrature demodulator adl5387 rev. 0 information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. specifications subject to change without notice. no license is granted by implication or otherwise under any patent or patent rights of analog devices. trademarks and registered trademarks are the property of their respective owners. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781.329.4700 www.analog.com fax: 781.461.3113 ?2007 analog devices, inc. all rights reserved. features operating rf frequency 50 mhz to 2 ghz lo input at 2 f lo 100 mhz to 4 ghz input ip3: 31 dbm @ 900 mhz input ip2: 62 dbm @ 900 mhz input p1db: 13 dbm @ 900 mhz noise figure (nf) 12.0 db @ 140 mhz 14.7 db @ 900 mhz voltage conversion gain > 4 db quadrature demodulation accuracy phase accuracy ~0.4 amplitude balance ~0.05 db demodulation bandwidth ~240 mhz baseband i/q drive 2 v p-p into 200 single 5 v supply applications qam/qpsk rf/if demodulators w-cdma/cdma/cdma2000/gsm microwave point-to-(multi)point radios broadband wireless and wimax broadband catvs functional block diagram divide-by-2 phase splitter 1 24 cmrf cmrf rfip rfin cmrf vpx cml vpa com bias vpl vpl vpl vpb vpb qhi qlo ihi ilo loip loin cml cml com 23 22 21 20 19 789101112 2 3 4 5 6 18 17 16 15 14 13 06764-001 figure 1. general description the adl5387 is a broadband quadrature i/q demodulator that covers an rf/if input frequency range from 50 mhz to 2 ghz. with a nf = 13.2 db, ip1db = 12.7 dbm, and iip3 = 32 dbm @ 450 mhz, the adl5387 demodulator offers outstanding dynamic range suitable for the demanding infrastructure direct-conversion requirements. the differential rf/if inputs provide a well- behaved broadband input impedance of 50 and are best driven from a 1:1 balun for optimum performance. ultrabroadband operation is achieved with a divide-by-2 method for local oscillator (lo) quadrature generation. over a wide range of lo levels, excellent demodulation accuracy is achieved with amplitude and phase balances ~0.05 db and ~0.4, respectively. the demodulated in-phase (i) and quadrature (q) differential outputs are fully buffered and provide a voltage conversion gain of >4 db. the buffered baseband outputs are capable of driving a 2 v p-p differential signal into 200 . the fully balanced design minimizes effects from second-order distortion. the leakage from the lo port to the rf port is 60 dbm. the adl5387 operates off a single 4.75 v to 5.25 v supply. the supply current is adjustable with an external resistor from the bias pin to ground. the adl5387 is fabricated using the analog devices, inc. advanced silicon-germanium bipolar process and is available in a 24-lead exposed paddle lfcsp.
adl5387 rev. 0 | page 2 of 28 table of contents features .............................................................................................. 1 applications ....................................................................................... 1 functional block diagram .............................................................. 1 general description ......................................................................... 1 revision history ............................................................................... 2 specifications ..................................................................................... 3 absolute maximum ratings ............................................................ 5 esd caution .................................................................................. 5 pin configuration and function descriptions ............................. 6 typical performance characteristics ............................................. 7 distributions for f rf = 140 mhz ............................................... 10 distributions for f rf = 450 mhz ............................................... 11 distributions for f rf = 900 mhz ............................................... 12 distributions for f rf = 1900 mhz ............................................. 13 circuit description ......................................................................... 14 lo interface ................................................................................. 14 v-to-i converter ......................................................................... 14 mixers .......................................................................................... 14 emitter follower buffers ........................................................... 14 bias circuit .................................................................................. 14 applications ..................................................................................... 15 basic connections ...................................................................... 15 power supply ............................................................................... 15 local oscillator (lo) input ...................................................... 15 rf input ....................................................................................... 16 baseband outputs ...................................................................... 16 error vector magnitude (evm) performance ....................... 17 low if image rejection ............................................................. 18 example baseband interface ..................................................... 18 characterization setups ................................................................. 21 evaluation board ............................................................................ 23 outline dimensions ....................................................................... 26 ordering guide .......................................................................... 26 revision history 10/07revision 0: initial version
adl5387 rev. 0 | page 3 of 28 specifications v s = 5 v, t a = 25c, f rf = 900 mhz, f if = 4.5 mhz, p lo = 0 dbm, bias pin open, z o = 50 , unless otherwise noted, baseband outputs differentially loaded with 450 . table 1. parameter condition min typ max unit operating conditions lo frequency range external input = 2xlo frequency 0.1 4 ghz rf frequency range 0.05 2 ghz lo input loip, loin input return loss ac-coupled into loip with loin bypassed, measured at 2 ghz ?10 db lo input level ?6 0 +6 dbm i/q baseband outputs qhi, qlo, ihi, ilo voltage conversion gain 450 differential load on i and q outputs (@ 900 mhz) 4.3 db 200 differential load on i and q outputs (@ 900 mhz) 3.2 db demodulation bandwidth 1 v p-p signal 3 db bandwidth 240 mhz quadrature phase error @ 900 mhz 0.4 degrees i/q amplitude imbalance 0.1 db output dc offset (differential) 0 dbm lo input 5 mv output common-mode vpos ? 2.8 v 0.1 db gain flatness 40 mhz output swing differential 200 load 2 v p-p peak output current each pin 12 ma power supplies vpa, vpl, vpb, vpx voltage 4.75 5.25 v current bias pin open 180 ma rbias = 4 k 157 ma dynamic performance @ rf = 140 mhz rfip, rfin conversion gain 4.7 db input p1db (ip1db) 13 dbm second-order input intercept (iip2) ?5 dbm each input tone 67 dbm third-order input intercept (iip3) ?5 dbm each input tone 31 dbm lo to rf rfin, rfip terminated in 50 , 1xlo appearing at the rf port ?100 dbm rf to lo loin, loip terminated in 50 ?95 dbc i/q magnitude imbalance 0.05 db i/q phase imbalance 0.2 degrees lo to i/q rfin, rfip terminated in 50 , 1xlo appearing at the bb port ?39 dbm noise figure 12.0 db noise figure under blocking conditions with a ?5 dbm interferer 5 mhz away 14.4 db
adl5387 rev. 0 | page 4 of 28 parameter condition min typ max unit dynamic performance @ rf = 450 mhz conversion gain 4.4 db input p1db (ip1db) 12.7 dbm second-order input intercept (iip2) ?5 dbm each input tone 69.2 dbm third-order input intercept (iip3) ?5 dbm each input tone 32.8 dbm lo to rf rfin, rfip terminated in 50 , 1xlo appearing at the rf port ?87 dbm rf to lo loin, loip terminated in 50 ?90 dbc i/q magnitude imbalance 0.05 db i/q phase imbalance 0.6 degrees lo to i/q rfin, rfip terminated in 50 , 1xlo appearing at the bb port ?38 dbm noise figure 13.2 db dynamic performance @ rf = 900 mhz conversion gain 4.3 db input p1db (ip1db) 12.8 dbm second-order input intercept (iip2) ?5 dbm each input tone 61.7 dbm third-order input intercept (iip3) ?5 dbm each input tone 31.2 dbm lo to rf rfin, rfip terminated in 50 , 1xlo appearing at the rf port ?79 dbm rf to lo loin, loip terminated in 50 ?88 dbc i/q magnitude imbalance 0.05 db i/q phase imbalance 0.2 degrees lo to i/q rfin, rfip terminated in 50 , 1xlo appearing at the bb port ?41 dbm noise figure 14.7 db noise figure under blocking conditions with a ?5 dbm interferer 5 mhz away 15.8 db dynamic performance @ rf = 1900 mhz conversion gain 3.8 db input p1db (ip1db) 12.8 dbm second-order input intercept (iip2) ?5 dbm each input tone 59.8 dbm third-order input intercept (iip3) ?5 dbm each input tone 27.4 dbm lo to rf rfin, rfip terminated in 50 , 1xlo appearing at the rf port ?75 dbm rf to lo loin, loip terminated in 50 ?70 dbc i/q magnitude imbalance 0.05 db i/q phase imbalance 0.3 degrees lo to i/q rfin, rfip terminated in 50 , 1xlo appearing at the bb port ?43 dbm noise figure 16.5 db noise figure under blocking conditions with a ?5 dbm interferer 5 mhz away 18.7 db
adl5387 rev. 0 | page 5 of 28 absolute maximum ratings table 2. parameter rating supply voltage vpos1, vpos2, vpos3 5.5 v lo input power 13 dbm (re: 50 ) rf/if input power 15 dbm (re: 50 ) internal maximum power dissipation 1100 mw ja 54c/w maximum junction temperature 150c operating temperature range ?40c to +85c storage temperature range ?65c to +125c stresses above those listed under absolute maximum ratings may cause permanent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. esd caution
adl5387 rev. 0 | page 6 of 28 pin configuration and fu nction descriptions 1 24 cmrf cmrf rfip adl5387 top view (not to scale) rfin cmrf vpx cml vpa com bias vpl vpl vpl vpb vpb qhi qlo ihi ilo loip loin cml cml com 23 22 21 20 19 789101112 2 3 4 5 6 18 17 16 15 14 13 06764-002 figure 2. pin configuration table 3. pin function descriptions pin o. neonic description 1, 4 to 6, 17 to 19 vpa, vpl, vpb, vpx supply. positive supply for lo, if, biasing and baseband sections, respectively. these pins should be decoupled to board ground using appropriate sized capacitors. 2, 7, 10 to 12, 20, 23, 24 com, cml, cmrf ground. connect to a low impedance ground plane. 3 bias bias control. a resistor can be connected between bias and com to reduce the mixer core current. the default setting for this pin is open. 8, 9 loip, loin local oscillator. external lo input is at 2xlo freq uency. a single-ended lo at 0 dbm can be applied through a 1000 pf capacitor to loip. loin should be ac-grounded, also using a 1000 pf. these inputs can also be driven differentially through a ba lun (recommended balun is m/a-com etc1-1-13). 13 to 16 ilo, ihi, qlo, qhi i-channel and q-channel mixer baseband outputs. these outputs have a 50 differential output impedance (25 per pin). the bias level on these pins is equal to vpos ? 2.8 v. each output pair can swing 2 v p-p (differential) into a load of 200 . output 3 db bandwidth is 240 mhz. 21, 22 rfin, rfip rf input. a single-ended 50 signal can be applied to the rf inputs through a 1:1 balun (recommended balun is m/a-com etc1-1-13). ground-referenced inductors must also be connected to rfip and rfin (recommended values = 120 nh). ep exposed paddle. connect to a low impedance ground plane
adl5387 rev. 0 | page 7 of 28 typical performance characteristics v s = 5 v, t a = 25c, lo drive level = 0 dbm, r bias = open, unless otherwise noted. 20 15 10 5 0 0 200 400 600 800 1000 1200 1400 1600 1800 2000 gain (db), ip1db (dbm) rf frequency (mhz) gain input p1db t a = +85c t a = +25c t a = ?40c 06764-003 figure 3. conversion gain and input 1 db compression point (ip1db) vs. rf frequency 80 70 50 30 60 40 20 10 0 200 400 600 800 1000 1200 1400 1600 1800 2000 iip2, iip3 (dbm) rf frequency (mhz) t a = ?40c t a = +25c t a = +85c q channel i channel input ip3 (i and q channels) input ip2 06764-004 figure 4. input third-order intercept (iip3) and input second-order intercept point (iip2) vs. rf frequency 2.0 1.5 1.0 0.5 0 ?0.5 ?1.0 ?1.5 ?2.0 0 200 400 600 800 1000 1200 1400 1600 1800 2000 magnitude error (db) rf frequency (mhz) t a = +85c t a = +25c t a = ?40c 06764-005 figure 5. i/q gain mism atch vs. rf frequency 5 ?30 ?25 ?20 ?15 ?10 ?5 0 1 1000 100 10 bb response (db) bb frequency (mhz) 06764-006 normalized to 1mhz figure 6. normalized i/q baseband frequency response 19 17 15 13 11 9 7 0 200 400 600 800 1000 1200 1400 1600 1800 2000 noise figure (db) rf frequency (mhz) t a = +85c t a = +25c t a = ?40c 06764-007 figure 7. noise figure vs. rf frequency 4 3 2 1 0 ?1 ?2 ?3 ?4 0 200 400 600 800 1000 1200 1400 1600 1800 2000 quadrature phase error (degrees) rf frequency (mhz) t a = +85c t a = +25c t a = ?40c 06764-008 figure 8. i/q quadrature phase error vs. rf frequency
adl5387 rev. 0 | page 8 of 28 20 15 10 5 0 ?6?5?4?3?2?10123456 gain (db), input p1db (dbm), noise figure (db) 80 65 50 35 20 input ip2, input ip3 (dbm) lo level (dbm) input ip2, q channel input p1db gain input ip3 noise figure input ip2, i channel 06764-009 figure 9. conversion gain, noise figure, iip3, iip2, and ip1db vs. lo level, f rf = 140 mhz 32 28 24 20 16 12 8 1 10 100 iip3 (dbm) and noise figure (db) 195 135 145 155 165 175 185 supply current (ma) r bias (k ? ) input ip3 noise figure supply current t a = +85c t a = +25c t a = ?40c 06764-010 figure 10. noise figure, iip3, and supply current vs. r bias , f rf = 140 mhz 25 20 15 10 5 0 ?30 5 0 ?5 ?10 ?15 ?20 ?25 noise figure (db) rf blocker input power (dbm) r bias = 100k ? r bias = 10k ? r bias = 4k ? r bias = 1.4k ? 06764-011 figure 11. noise figure vs. input blocker level, f rf = 900 mhz (rf blocker 5 mhz offset) 20 15 10 5 0 ?6?5?4?3?2?10123456 gain (db), input p1db (dbm), noise figure (db) 80 65 50 35 20 input ip2, input ip3 (dbm) lo level (dbm) input ip2, i channel input p1db gain input ip3 noise figure input ip2, q channel 06764-012 figure 12. conversion gain, noise figure, iip3, iip2, and ip1db vs. lo level, f rf = 900 mhz 32 28 24 20 16 12 8 11 0 iip3 (dbm) and noise figure (db) r bias (k ? ) 1 0 0 input ip3 noise figure t a = +85c t a = +25c t a = ?40c 06764-013 figure 13. iip3 and noise figure vs. r bias , f rf = 900 mhz 80 70 60 50 40 30 20 10 0 11 0 gain (db), ip1db, iip2, i and q channels (dbm) r bias (k ? ) 1 0 0 140mhz: gain 140mhz: ip1db 140mhz: iip2, i channel 140mhz: iip2, q channel 450mhz: gain 450mhz: ip1db 450mhz: iip2, i channel 450mhz: iip2, q channel 06764-014 figure 14. conversion gain, ip1db, iip 2 i channel, and iip2 q channel vs. r bias
adl5387 rev. 0 | page 9 of 28 35 30 25 20 15 10 5 05 0 4540353025201510 5 ip1db, iip3 (dbm) 80 50 55 60 65 70 75 input ip2, i and q channels (dbm) bb frequency (mhz) ? 20 ?30 ?40 ?50 ?60 ?70 ?80 ?90 ?100 0 2000 1800 1600 1400 1200 1000800600400200 lo leakage (dbm) internal 1xlo frequency (mhz) t a = +85c t a = +25c t a = ?40c iip3 input ip2, i channel input ip2, q channel ip1db 1xlo 2xlo 06764-015 06764-018 figure 15. iiip3, iip2, ip1db vs. baseband frequency 0 ?10 ?20 ?30 ?40 ?50 ?60 ?70 ?80 0 2000 1800 1600 1400 1200 1000800600400200 feedthrough (dbm) internal 1xlo frequency (mhz) 1xlo (internal) 2xlo (external) 06764-016 figure 16. lo-to-bb feedthrough vs. 1xlo frequency (internal lo frequency) 0 ?25 ?20 ?15 ?10 ?5 0 2000 1800 1600 1400 1200 1000800600400200 return loss (db) rf frequency (mhz) 06764-017 figure 17. rf port return loss vs. rf frequency, measured on characterization board through etc1-1-1 3 balun with 120 nh bias inductors figure 18. lo-to-rf leakage vs. internal 1xlo frequency ? 20 ?40 ?60 ?80 ?100 ?120 0 2000 1800 1600 1400 1200 1000800600400200 leakage (dbc) rf frequency (mhz) 06764-019 figure 19. rf-to-lo leakage vs. rf frequency 0 ?30 ?25 ?20 ?15 ?10 ?5 0 4000 3500 3000 2500 2000 1500 1000 500 return loss (db) frequency (mhz) 06764-020 figure 20. single-ended lo port return loss vs. lo frequency, loin ac-coupled to ground
adl5387 rev. 0 | page 10 of 28 distributions for f rf = 140 mhz 100 0 20 40 60 80 28 33 30 29 32 31 percentage (%) input ip3 (dbm) t a = +85c t a = +25c t a = ?40c 06764-021 figure 21. iip3 distributions 100 0 20 40 60 80 10 15 12 11 14 13 percentage (%) input p1db (dbm) t a = +85c t a = +25c t a = ?40c 06764-022 figure 22. ip1db distributions 100 0 20 40 60 80 ?0.2 0.2 0 ?0.1 0.1 percentage (%) i/q gain mismatch (db) t a = +85c t a = +25c t a = ?40c 06764-023 figure 23. i/q gain mismatch distributions 100 0 20 40 60 80 60 75 65 70 percentage (%) input ip2 (dbm) t a = +85c t a = +25c t a = ?40c q channel i channel 06764-024 figure 24. iip2 distributions for i channel and q channel 100 0 20 40 60 80 10.5 13.5 13.0 12.5 12.0 11.5 11.0 percentage (%) noise figure (db) t a = +85c t a = +25c t a = ?40c 06764-025 figure 25. noise figure distributions 100 0 20 40 60 80 ?1.0 1.0 0.5 0 ?0.5 percentage (%) quadrature phase error (degrees) t a = +85c t a = +25c t a = ?40c 06764-026 figure 26. i/q quadrature error distributions
adl5387 rev. 0 | page 11 of 28 distributions for f rf = 450 mhz 100 0 20 40 60 80 30 35 34 33 32 31 percentage (%) input ip3 (dbm) t a = +85c t a = +25c t a = ?40c 06764-027 figure 27. iip3 distributions 100 0 20 40 60 80 10 15 14 13 12 11 percentage (%) input p1db (dbm) t a = +85c t a = +25c t a = ?40c 06764-028 figure 28. ip1db distributions 100 0 20 40 60 80 ?0.2 0.2 0.1 0 ?0.1 percentage (%) i/q gain mismatch (db) t a = +85c t a = +25c t a = ?40c 06764-029 figure 29. i/q gain mismatch distributions 100 0 20 40 60 80 60 75 65 70 percentage (%) input ip2 (dbm) t a = +85c t a = +25c t a = ?40c q channel i channel 06764-030 figure 30. iip2 distributions for i channel and q channel 100 0 20 40 60 80 12.0 15.0 14.5 14.0 13.5 13.0 12.5 percentage (%) noise figure (db) t a = +85c t a = +25c t a = ?40c 06764-031 figure 31. noise figure distributions 100 0 20 40 60 80 ?1.0 ?0.5 0 0.5 1.0 percentage (%) quadrature phase error (degrees) t a = +85c t a = +25c t a = ?40c 06764-032 figure 32. i/q quadrature error distributions
adl5387 rev. 0 | page 12 of 28 distributions for f rf = 900 mhz 100 0 20 40 60 80 30 31 33 32 34 35 percentage (%) input ip3 (dbm) t a = +85c t a = +25c t a = ?40c 06764-033 figure 33. iip3 distributions 100 0 20 40 60 80 10 11 13 12 14 15 percentage (%) input p1db (dbm) t a = +85c t a = +25c t a = ?40c 06764-034 figure 34. ip1db distributions 100 0 20 40 60 80 ?0.2 ?0.1 0 0.1 0.2 percentage (%) i/q gain mismatch (db) t a = +85c t a = +25c t a = ?40c 06764-035 figure 35. i/q gain mismatch distributions 100 0 20 40 60 80 55 75 65 60 70 percentage (%) input ip2 (dbm) t a = +85c t a = +25c t a = ?40c q channel i channel 06764-036 figure 36. iip2 distributions for i channel and q channel 100 0 20 40 60 80 13.0 13.5 14.0 14.5 15.0 15.5 16.0 percentage (%) noise figure (db) t a = +85c t a = +25c t a = ?40c 06764-037 figure 37. noise figure distributions 100 0 20 40 60 80 ?1.0 1.0 0.5 0 ?0.5 percentage (%) quadrature phase error (degrees) t a = +85c t a = +25c t a = ?40c 06764-038 figure 38. i/q quadrature error distributions
adl5387 rev. 0 | page 13 of 28 distributions for f rf = 1900 mhz 100 0 20 40 60 80 26 31 29 30 28 27 percentage (%) input ip3 (dbm) t a = +85c t a = +25c t a = ?40c 06764-039 figure 39. iip3 distributions 100 0 20 40 60 80 10 15 13 14 12 11 percentage (%) input p1db (dbm) t a = +85c t a = +25c t a = ?40c 06764-040 figure 40. ip1db distributions 100 0 20 40 60 80 ?0.2 0.2 0.1 0 ?0.1 percentage (%) i/q gain mismatch (db) t a = +85c t a = +25c t a = ?40c 06764-041 figure 41. i/q gain mismatch distributions 100 0 20 40 60 80 52 6866646260585654 percentage (%) input ip2 (dbm) t a = +85c t a = +25c t a = ?40c q channel i channel 06764-042 figure 42. iip2 distributions for i channel and q channel 100 0 20 40 60 80 15.0 18.0 17.5 17.0 16.5 16.0 15.5 percentage (%) noise figure (db) t a = +85c t a = +25c t a = ?40c 06764-043 figure 43. noise figure distributions 100 0 20 40 60 80 ?1.0 1.0 0.5 0 ?0.5 percentage (%) quadrature phase error (degrees) t a = +85c t a = +25c t a = ?40c 06764-044 figure 44. i/q quadrature error distributions
adl5387 rev. 0 | page 14 of 28 circuit description the adl5387 can be divided into five sections: the local oscillator (lo) interface, the rf voltage-to-current (v-to-i) converter, the mixers, the differential emitter follower outputs, and the bias circuit. a detailed block diagram of the device is shown in figure 45 . rfip rfin bias divide-by-two quadrature phase splitter ihi ilo loip loin qhi qlo 0 6764-045 figure 45. block diagram the lo interface generates two lo signals at 90 of phase difference to drive two mixers in quadrature. rf signals are converted into currents by the v-to-i converters that feed into the two mixers. the differential i and q outputs of the mixers are buffered via emitter followers. reference currents to each section are generated by the bias circuit. a detailed description of each section follows. lo interface the lo interface consists of a buffer amplifier followed by a frequency divider that generate two carriers at half the input frequency and in quadrature with each other. each carrier is then amplified and amplitude-limited to drive the double- balanced mixers. v-to-i converter the differential rf input signal is applied to a resistively degenerated common base stage, which converts the differential input voltage to output currents. the output currents then modulate the two half-frequency lo carriers in the mixer stage. mixers the adl5387 has two double-balanced mixers: one for the in-phase channel (i channel) and one for the quadrature channel (q channel). these mixers are based on the gilbert cell design of four cross-connected transistors. the output currents from the two mixers are summed together in the resistive loads that then feed into the subsequent emitter follower buffers. emitter follower buffers the output emitter followers drive the differential i and q signals off-chip. the output impedance is set by on-chip 25 series resistors that yield a 50 differential output impedance for each baseband port. the fixed output impedance forms a voltage divider with the load impedance that reduces the effective gain. for example, a 500 differential load has 1 db lower effective gain than a high (10 k) differential load impedance. bias circuit a band gap reference circuit generates the proportional-to- absolute temperature (ptat) as well as temperature-independent reference currents used by different sections. the mixer current can be reduced via an external resistor between the bias pin and ground. when the bias pin is open, the mixer runs at maximum current and hence the greatest dynamic range. the mixer current can be reduced by placing a resistance to ground; therefore, reducing overall power consumption, noise figure, and iip3. the effect on each of these parameters is shown in figure 10 , figure 13 , and figure 14 .
adl5387 rev. 0 | page 15 of 28 applications information basic connections figure 47 shows the basic connections schematic for the adl5387. power supply the nominal voltage supply for the adl5387 is 5 v and is applied to the vpa, vpb, vpl, and vpx pins. ground should be connected to the com, cml, and cmrf pins. each of the supply pins should be decoupled using two capacitors; recommended capacitor values are 100 pf and 0.1 f. local oscillator (lo) input the lo port is driven in a single-ended manner. the lo signal must be ac-coupled via a 1000 pf capacitor directly into loip, and loin is ac-coupled to ground also using a 1000 pf capacitor. the lo port is designed for a broadband 50 match and therefore exhibits excellent return loss from 100 mhz to 4 ghz. the lo return loss can be seen in figure 20 . figure 46 shows the lo input configuration. lo input loip loin 1000pf 1000pf 8 9 06764-047 figure 46. single-ended lo drive the recommended lo drive level is between ?6 dbm and +6 dbm. the lo frequency at the input to the device should be twice that of the desired lo frequency at the mixer core. the applied lo frequency range is between 100 mhz and 4 ghz. rfc 120nh 120nh 1000pf 1000pf 100pf 100pf 0.1f 1000pf 100pf 1000pf 0.1f 0.1f v pos v pos lo v pos etc1-1-13 1 adl5387 cmrf cmrf rfip rfin cmrf vpx cml loip loin cml cml com 24 23 22 21 20 19 789101112 2 3 4 5 6 vpa com bias vpl vpl vpl 18 17 16 15 14 13 vpb qhi qlo ihi ilo vpb qhi qlo ihi ilo 06764-046 figure 47. basic connections schematic for adl5387
adl5387 rev. 0 | page 16 of 28 rf input the rf inputs have a differential input impedance of approximately 50 . for optimum performance, the rf port should be driven differentially through a balun. the recommended balun is m/a-com etc1-1-13. the rf inputs to the device should be ac-coupled with 1000 pf capacitors. ground-referenced choke inductors must also be connected to rfip and rfin (recommended value = 120 nh, coilcraft 0402cs-r12xjl) for appropriate biasing. several important aspects must be taken into account when selecting an appropriate choke inductor for this application. first, the inductor must be able to handle the approximately 40 ma of standing dc current being delivered from each of the rf input pins (rfip, rfin). (the suggested 0402 inductor has a 50 ma current rating). the purpose of the choke inductors is to provide a very low resistance dc path to ground and high ac impedance at the rf frequency so as not to affect the rf input impedance. a choke inductor that has a self- resonant frequency greater than the rf input frequency ensures that the choke is still looking inductive and therefore has a more predictable ac impedance (jl) at the rf frequency. figure 48 shows the rf input configuration. rf input rfin etc1-1-13 120nh 120nh rfip 1000pf 1000pf 21 22 06764-048 figure 48. rf input the differential rf port return loss has been characterized as shown in figure 49 . ? 10 ?12 ?14 ?16 ?18 ?20 ?22 ?24 ?26 ?28 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 s(1, 1) (db) frequency (ghz) 06764-049 figure 49. differential rf port return loss baseband outputs the baseband outputs qhi, qlo, ihi, and ilo are fixed impedance ports. each baseband pair has a 50 differential output impedance. the outputs can be presented with differential loads as low as 200 (with some degradation in linearity and gain) or high impedance differential loads (500 or greater impedance yields the same excellent linearity) that is typical of an adc. the tcm9-1 9:1 balun converts the differential if output to single-ended. when loaded with 50 , this balun presents a 450 load to the device. the typical maximum linear voltage swing for these outputs is 2 v p-p differential. the bias level on these pins is equal to vpos ? 2.8 v. the output 3 db bandwidth is 240 mhz. figure 50 shows the baseband output configuration. qhi qlo ihi ilo qhi qlo ihi ilo 16 15 14 13 06764-050 figure 50. baseband output configuration
adl5387 rev. 0 | page 17 of 28 error vector magnitude (evm) performance evm is a measure used to quantify the performance of a digital radio transmitter or receiver. a signal received by a receiver would have all constellation points at the ideal locations; however, various imperfections in the implementation (such as carrier leakage , phase noise , and quadrature error) cause the actual constellation points to deviate from the ideal locations. the adl5387 shows excellent evm performance for various modulation schemes. figure 51 shows typical evm performance over input power range for a point-to-point application with 16 qam modulation schemes and zero-if baseband. the differential dc offsets on the adl5387 are in the order of a few mv. however, ac coupling the baseband outputs with 10 f capacitors helps to eliminate dc offsets and enhances evm performance. with a 10 mhz bw signal, 10 f ac coupling capacitors with the 500 differential load results in a high-pass corner frequency of ~64 hz which absorbs an insignificant amount of modulated signal energy from the baseband signal. by using ac coupling capacitors at the baseband outputs, the dc offset effects, which can limit dynamic range at low input power levels, can be eliminated. 0 ?50 ?45 ?40 ?35 ?30 ?25 ?20 ?15 ?10 ?5 ?70 10 0 ?10 ?20 ?30 ?40 ?50 ?60 evm (db) input power (dbm) 06764-051 figure 51. rf = 140 mhz, if = 0 hz, evm vs. input power for a 16 qam 10 msym/s signal (ac-coupled baseband outputs) figure 52 shows the evm performance of the adl5387 when ac-coupled, with an ieee 802.16e wimax signal. 0 ?50 ?45 ?40 ?35 ?30 ?25 ?20 ?15 ?10 ?5 ?50 20 10 0 ?10 ?20 ?30 ?40 evm (db) input power (dbm) 06764-052 figure 52. rf = 750mhz mhz, if = 0 hz, evm vs. input power for a 16 qam 10 mhz bandwidth mobile wimax signal (ac-coupled baseband outputs) figure 53 exhibits the zero if evm performance of a wcdma signal over a wide rf input power range. 0 ?45 ?40 ?35 ?30 ?25 ?20 ?15 ?10 ?5 ?70 ?60 10 0 ?10 ?20 ?30 ?40 ?50 evm (db) input power (dbm) 06764-053 figure 53. rf = 1950 mhz, if = 0 hz, evm vs. input power for a wcdma (ac-coupled baseband outputs)
adl5387 rev. 0 | page 18 of 28 06764-054 0 0 sin lo t cos lo t if if lsb usb ? if 0+ if 0+ if 0+ if ? if 0+ if lo ?90 +90 figure 54. illustration of the image problem low if image rejection the image rejection ratio is the ratio of the intermediate frequency (if) signal level produced by the desired input frequency to that produced by the image frequency . the image rejection ratio is expressed in decibels . appropriate image rejection is critical because the image power can be much higher than that of the desired signal, thereby plaguing the down conversion process. figure 54 illustrates the image problem. if the upper sideband (lower sideband) is the desired band, a 90 shift to the q channel (i channel) cancels the image at the lower sideband (upper sideband). figure 55 shows the excellent image rejection capabilities of the adl5387 for low if applications, such as cdma2000. the adl5387 exhibits image rejection greater than 45 db over the broad frequency range for an if = 1.23 mhz. 0 ?70 ?60 ?50 ?40 ?30 ?20 ?10 50 250 450 650 850 1050 1250 1450 1650 1850 image rejection at 1.23mhz (db) rf input frequency (mhz) 06764-055 figure 55. image rejection vs. rf input frequency for a cdma2000 signal, if = 1.23 mhz example baseband interface in most direct conversion receiver designs, it is desirable to select a wanted carrier within a specified band. the desired channel can be demodulated by tuning the lo to the appropriate carrier frequency. if the desired rf band contains multiple carriers of interest, the adjacent carriers would also be down converted to a lower if frequency. these adjacent carriers can be problematic if they are large relative to the wanted carrier as they can overdrive the baseband signal detection circuitry. as a result, it is often necessary to insert a filter to provide sufficient rejection of the adjacent carriers. it is necessary to consider the overall source and load impedance presented by the adl5387 and adc input to design the filter network. the differential baseband output impedance of the adl5387 is 50 . the adl5387 is designed to drive a high impedance adc input. it may be desirable to terminate the adc input down to lower impedance by using a terminating resistor, such as 500 . the terminating resistor helps to better define the input impedance at the adc input. the order and type of filter network depends on the desired high frequency rejection required, pass-band ripple, and group delay. filter design tables provide outlines for various filter types and orders, illustrating the normalized inductor and capacitor values for a 1 hz cutoff frequency and 1 load. after scaling the normalized prototype element values by the actual desired cut-off frequency and load impedance, the series reactance elements are halved to realize the final balanced filter network component values.
adl5387 rev. 0 | page 19 of 28 as an example, a second-order, butterworth, low-pass filter design is shown in figure 56 where the differential load impedance is 500 , and the source impedance of the adl5387 is 50 . the normalized series inductor value for the 10-to-1, load-to- source impedance ratio is 0.074 h, and the normalized shunt capacitor is 14.814 f. for a 10.9 mhz cutoff frequency, the single-ended equivalent circuit consists of a 0.54 h series inductor followed by a 433 pf shunt capacitor. the balanced configuration is realized as the 0.54 h inductor is split in half to realize the network shown in figure 56 . 06764-056 v s r s 2 r s r l r s 2 r l 2 r l 2 433pf v s r s = 50 ? r l = 500 ? 0.54h 0.27h 0.27h 433pf balanced configuration denormalized single-ended equivalent v s r s = 50 ? = 0.1 r l = 500 ? l n = 0.074h c n 14.814f normalized single-ended configuration = 25 ? = 25 ? = 250 ? = 250 ? f c = 10.9mhz f c = 1hz figure 56. second-order, butterworth, low-pass filter design example a complete design example is shown in figure 59 . a sixth-order butterworth differential filter having a 1.9 mhz corner frequency interfaces the output of the adl5387 to that of an adc input. the 500 load resistor defines the input impedance of the adc. the filter adheres to typical direct conversion wcdma applications, where 1.92 mhz away from the carrier if frequency, 1 db of rejection is desired and 2.7 mhz away 10 db of rejection is desired. figure 57 and figure 58 show the measured frequency response and group delay of the filter. 10 5 ?20 ?15 ?10 ?5 0 03 3.0 2.5 2.0 1.5 1.0 0.5 magnitude response (db) frequency (mhz) 06764-157 . 5 figure 57. baseband filter response 900 800 700 600 500 400 300 200 100 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 delay (ns) frequency (mhz) 06764-158 figure 58. baseband filter group delay
adl5387 rev. 0 | page 20 of 28 06764-159 rfc 1000pf 100pf 0.1f 1000pf 100pf 0.1f 0.1f 100pf v pos v pos lo 1000pf 1000pf v pos etc1-1-13 1 adl5387 cmrf cmrf rfip rfin cmrf vpx cml loip loin cml cml com 24 23 22 21 20 19 7 8 9 10 11 12 2 3 4 5 6 vpa com bias vpl vpl vpl 18 17 16 15 14 13 vpb vpb qhi qlo ihi ilo 120nh 120nh c ac 10f c ac 10f 27h 27h 270pf 27h 27h 91pf 10h 10h 68pf 500? c ac 10f c ac 10f 27h 27h 270pf 27h 27h 91pf 10h 10h 68pf 500 ? adc input adc input figure 59. sixth order low-pass butte rworth baseband filter schematic
adl5387 rev. 0 | page 21 of 28 characterization setups figure 60 to figure 62 show the general characterization bench setups used extensively for the adl5387. the setup shown in figure 62 was used to do the bulk of the testing and used sinusoidal signals on both the lo and rf inputs. an automated agilent- vee program was used to control the equipment over the ieee bus. this setup was used to measure gain, ip1db, iip2, iip3, i/q gain match, and quadrature error. the adl5387 characterization board had a 9-to-1 impedance transformer on each of the differential baseband ports to do the differential-to-single- ended conversion. the two setups shown in figure 60 and figure 61 were used for making nf measurements. figure 60 shows the setup for measuring nf with no blocker signal applied while figure 61 was used to measure nf in the presence of a blocker. for both setups, the noise was measured at a baseband frequency of 10 mhz. for the case where a blocker was applied, the output blocker was at 15 mhz baseband frequency. note that great care must be taken when measuring nf in the presence of a blocker. the rf blocker generator must be filtered to prevent its noise (which increases with increasing generator output power) from swamping the noise contribution of the adl5387. at least 30 db of attention at the rf and image frequencies is desired. for example, with a 2xlo of 1848 mhz applied to the adl5387, the internal 1xlo is 924 mhz. to obtain a 15 mhz output blocker signal, the rf blocker generator is set to 939 mhz and the filters tuned such that there is at least 30 db of attenuation from the generator at both the desired rf frequency (934 mhz) and the image rf frequency (914 mhz). finally, the blocker must be removed from the output (by the 10 mhz low-pass filter) to prevent the blocker from swamping the analyzer. hp 6235a power supply agilent 8665b signal generator ieee ieee pc controller control sns output agilent n8974a noise figure analyzer 6db pad adl5387 char board rf lo q i gnd v pos low-pass filter input r1 50 ? from sns port 06764-057 figure 60. general noise figure measurement setup
adl5387 rev. 0 | page 22 of 28 r&s fsea30 spectrum analyzer hp 6235a power supply agilent 8665b signal generator low-pass filter r&s smt03 signal generator adl5387 char board rf lo q i gnd v pos 6db pad 6db pad 6db pad r1 50 ? band-pass cavity filter band-pass tunable filter band-reject tunable filter hp87405 low noise preamp 06764-058 figure 61. measurement setup for noise figure in the presence of a blocker 06764-059 r&s fsea30 spectrum analyzer hp 8508a vector voltmeter r&s smt-06 agilent e3631 pwer supply agilent e8257d signal generator pc controller r&s smt-06 ieee ieee ieee ieee ieee ieee adl5387 char board rf lo q i gnd v pos 6db pad 6db pad 6db pad 6db pad switch matrix rf amplifier vp gnd out in 3db pad 3db pad 3db pad 3db pad rf rf agilent 11636a input channels a and b rf input ieee figure 62. general adl5387 characterization setup
adl5387 rev. 0 | page 23 of 28 evaluation board the adl5387 evaluation board is available. the board can be used for single-ended or differential baseband analysis. the default configuration of the board is for single-ended baseband analysis. rfc c11 c8 r14 r16 r10 c12 r15 t2 t3 r9 r11 c9 c10 c2 c1 c3 c4 r1 r2 v pos v pos lo c5 c7 c6 r17 v pos t1 t4 1 adl5387 cmrf cmrf rfip rfin cmrf vpx cml loip loin cml cml com 24 23 22 21 20 19 7 8 9 101112 2 3 4 5 6 vpa com bias vpl vpl vpl 18 17 16 15 14 13 vpb q output or qhi qlo i output or ihi ilo vpb qhi qlo ihi ilo r8 r7 l2 l1 r6 r3 r4 r13 c13 r5 r12 0 6764-060 figure 63. evaluation board schematic
adl5387 rev. 0 | page 24 of 28 table 4. evaluation board configuration options component function default condition vpos, gnd power supply and ground vector pins. not applicable r1, r3, r6 power supply decoupling. shorts or power supply decoupling resistors. r1, r3, r6 = 0 (0805) c1, c2, c3, c4, c8, c9 the capacitors provide the required dc coupling up to 2 ghz. c2, c4, c8 = 100 pf (0402) c1, c3, c9 = 0.1 f (0603) c5, c6, c7, c10, c11 ac coupling capacitors. these capacitors provide the required ac coupling from 50 mhz to 2 ghz. c5, c6, c10, c11 = 1000 pf (0402), c7 = open r4, r5, r9 to r16 single-ended baseband output path. this is the default configuration of the evaluation board. r14 to r16 and r4, r5, and r13 are populated for appropriate balun interface. r9, r10 and r11, r12 are not populated. base band outputs are taken from qhi and ihi. the user can reconfigure the board to use fu ll differential baseband outputs. r9 to r12 provide a means to bypass the 9:1 tcm9-1 transformer to allow for differential baseband outputs. access the differential baseband signals by populating r9 to r12 with 0 and not populating r4, r5, r13 to r16. this way the transformer does not need to be removed. the baseband outputs are taken from the smas of q_hi, q_lo, i_hi, and i_lo. r4, r5, r13 to r16 = 0 (0402), r9 to r12 = open l1, l2, r7, r8 input biasing. inductance and resistance se ts the input biasing of the common base input stage. default value is 120 nh. l1, l2 = 120 nh (0402) r7, r8 = 0 (0402) t2, t3 if output interface. tcm9-1 converts a differential high impedance if output to a single- ended output. when loaded with 50 , this balun presents a 450 load to the device. the center tap can be decoupled through a capacitor to ground. t2, t3 = tcm9-1, 9:1 (mini-circuits) c12, c13 decoupling capacitors. c12 and c13 are the deco upling capacitors used to reject noise on the center tap of the tcm9-1. c12, c13 = 0.1 f (0402) r17 lo input interface. the lo is driven as a single-ended signal. although, there is no performance change for a differential signal drive, the option is available by placing a transformer (t4, etc1-1-13) on the lo input path. r17 = 0 (0402) t1 rf input interface. etc1-1-13 is a 1:1 rf balu n that converts the single-ended rf input to differential signal. t1 = etc1-1-13, 1:1 (m/a com) r2 r bias . optional bias setting resistor. see the bias circuit section to see how to use this feature. r2 = open
adl5387 rev. 0 | page 25 of 28 06764-164 figure 64. evaluation board top layer 06764-165 figure 65. evaluation board top layer silkscreen 06764-166 figure 66. evaluation board bottom layer 06764-167 figure 67. evaluation board bottom layer silkscreen
adl5387 rev. 0 | page 26 of 28 outline dimensions * compliant to jedec standards mo-220-vggd-2 except for exposed pad dimension 1 24 6 7 13 19 18 12 * 2.45 2.30 sq 2.15 0.60 max 0.50 0.40 0.30 0.30 0.23 0.18 2.50 ref 0.50 bsc 12 max 0.80 max 0.65 typ 0.05 max 0.02 nom 1.00 0.85 0.80 seating plane pin 1 indicator top view 3.75 bsc sq 4.00 bsc sq pin 1 indicator 0.60 max coplanarity 0.08 0.20 ref 0.23 min exposed pa d (bottomview) figure 68. 24-lead lead frame chip scale package [lfcsp_vq] 4 mm 4 mm body, very thin quad (cp-24-2) dimensions shown in millimeters ordering guide model temperature range package descript ion package option ordering quantity adl5387acpz-r7 1 C40c to +85c 24-lead lfcsp_vq, 7 tape and reel cp-24-2 1,500 adl5387acpz-wp 1 C40c to +85c 24-lead lfcsp_vq, waffle pack cp-24-2 64 adl5387-evalz 1 evaluation board 1 z = rohs compliant part.
adl5387 rev. 0 | page 27 of 28 notes
adl5387 rev. 0 | page 28 of 28 notes ?2007 analog devices, inc. all rights reserved. trademarks and registered trademarks are the property of their respective owners. d06764-0-10/07(0)

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